No but drifting crossover distortion may be when cool, then thermal runaway risk exists if biased too much. Thermal runaway is mitigated by the 0.33 Ohm emitter resistors, so if the voltage drop in Vbe becomes less than the voltage rise due to current across the Re, you get more DC bias which leads to more Vbe drop and more Ic leading to thermal runaway and self destruction.
The risk is low due to a healthy large Re, but still exists at worst case output power loading. This emitter Re also compromises your dampening factor or inverse of load regulation as the bass reflex pushes current in the opposite direction when a change in voltage occurs at series resonance. Thus your dampening factor depends on negative feedback gain, and output impedance with minimum at 4 ohms ( about twice DCR of coils) Zsp*Av/(Re+Rbe)= 4*23/(0.33+?)< 273 which in between minimum and great (100-1000).
I have found the optimal DF, thermal runaway point uses temp compensated bias like Nakamichi with the minimum Re just slightly higher than the Rbe bulk resistance which one can compute from datasheets above saturation. The same is true for wiring Power LEDS in parallel, by adding an equalization R, often just long wire resistance to compensate for variations in ESR of the power diode, which is approximately ESR<=1/W power rating of the diode junction ( true for any type of diode from 75 mW to 750W or whatever... they dont teach you this in school or industry) This assumes adequately low Rja thermal resistance which affects the safety margin. I choose 10 % variation of Rbe which depends on quality of parts and heatsink Rja.
When current sharing any parallel devices, the product of Rja and Vpn for the diode based on -mV/'C and power capacity of Vbe or Vpn for power LEDs will determine value of series R, such 0.1Ω for 1W LEDs or 0.33Ω for Rbe for your PA based on power rating of Vbe junction. However I choose LEDs with tight tolerances on Vf, so wire resistance is often sufficient.
This means if you had temp and offset compensation, you could reduce losses and increase DF.
FYI only on your next bigger and better design,!
edit...
What this also means is your power supply must be lower ESR than your PA output impedance otherwise distortion and DF are degraded.
Since Zo = (Re (+Rbe))/ Av = 0.33/23 =23 mΩ. , which includes ESR of your big cap and wire R and inductive reactance.
Since Rbe rises rapidly with temp, its value with AC+DC current approaching your Re fix value, then add your ESR of V+- , from Cap aging and layout, your DF will be much lower than theoretical max of 273 and in fact may drop below 100 unless your verify ESR of the nice big cap.
edit.. new epcos 100k uF 50V caps are rated at 6.8mΩ when new. This means your bridge diode peak current or Pd may be exceeded if not designed for power-on surge time. I would verify ESR, bridge ESR, compute RC energy during power on and consider surge limiter. Some use relay bypass over fixed R, others use inexpensive NTC ICL's for desired current limits. Without this design improvement, stress factors on Cap, bridge reliability reduce MTBF rapidly. Consider 30Vp turn on into xx mΩ total ESR will saturate transformer secondary thus putting heat stress on turnon to part with highest ESR. When secondary saturates, Lm drops dramatically and causes Transformer wires to buzz on startup adding more vibration and heat stress to wire insulation. so consider ESR in everything on overall design and consider Short limiter and or short Circuit protection in your design. Some use fan cooled polyfuse to detect fan failure, others tach voltage or proper convection design.